Interleaved converter

ABSTRACT

The present invention includes: an input voltage detector detecting an input voltage of a parallel converter and outputting an input voltage signal; an output voltage detector detecting an output voltage of the parallel converter; and a controller. The controller includes an error amplifier comparing the output voltage signal and a reference voltage and outputting an error amplification signal; an arithmetic operator generating an ON time signal and an OFF time signal based on the input and output voltage signals and the error amplification signal; a phase signal generator generating plural phase signals having different phases based on the ON and OFF time signals and the error amplification signal; a pulse generator generating plural pulse-train signals synchronized with the respective phase signals based on the ON time signal, the error amplification signal and the phase signals; and a driver driving the switching units in accordance with the pulse-train signals.

TECHNICAL FIELD

The present invention relates to an interleaved converter, andparticularly, to a technique of a controller for the interleavedconverter.

BACKGROUND ART

An interleaved converter is disclosed in, for example, Japanese PatentApplication Publication Nos. Sho 62-58871 and Sho 63-186555 as well asJapanese Patent No. 3570113. The interleaved converter is an electricpower conversion device in which multiple converters are connected inparallel and are phase-shifted from one another to reduce currentripples of the current inputted to the converter and the current to beoutputted from the converter. In addition, a phase controller for aninterleaved converter is disclosed in Japanese Patent Nos. 3570113 and3480201.

FIG. 1 is a circuit configuration diagram showing a conventionalinterleaved converter using two circuits of boost converters.

In FIG. 1, a first series circuit, which includes a boost reactor L1, aswitching element Q1 made of a MOSFET, and a switching current detectorCT1, is connected to the terminals of an input power source Vin formedof a DC power source. The anode of a rectifier D1 is connected to aconnection point of the reactor L1 and the switching element Q1 whilethe cathode of the rectifier D1 is grounded through a smoothingcapacitor Co.

A second series circuit, which includes a boost reactor L2, a switchingelement Q2 made of a MOSFET, and a switching current detector CT2, isconnected to the terminals of the input power source Vin. The anode of arectifier D2 is connected to a connection point of the boost reactor L2and the switching element Q2 while the cathode of the rectifier D2 isgrounded through the smoothing capacitor Co.

A voltage detector 20 is configured to receive an output voltage Vooutputted from the terminals of the smoothing capacitor Co, and outputan output voltage signal VFB. A first control circuit 21 is configuredto generate an output signal Vdr1 based on an output from the switchingcurrent detector CT1 and the output voltage signal VFB, and therebyperform on/off control of the gate of the switching element Q1 by usingthe output signal Vdr1. A charge/discharge device 23 is configured toreceive the output signal Vdr1 from the first control circuit 21. Aphase control capacitor C21 is connected to one of output terminals ofthe charge/discharge device 23 and a phase control capacitor C22 isconnected to the other one of the output terminals of thecharge/discharge device 23.

A second control circuit 22 is configured to generate an output signalVdr2 based on an output Vi2 from the switching current detector CT2, theoutput voltage signal VFB, as well as outputs Vc1 and Vc2 of the phasecontrol capacitors C21 and C22, and thereby perform on/off control ofthe gate of the switching element Q2 by using the output signal Vdr2.

The boost reactor L1, the switching element Q1, the switching currentdetector CT1, the rectifier D1, and the first control circuit 21 form afirst converter. The boost reactor L2, the switching element Q2, theswitching current detector CT2, the rectifier D2, and the second controlcircuit 22 form a second converter. The first converter and the secondconverter are connected to each other at the respective input terminalsas well as at the respective output terminals, thereby forming a boostinterleaved converter.

The boost converter is configured to output an output voltage Vo that ishigher than an input voltage Vin in accordance with the ON/OFFoperations of the switching elements Q1 and Q2. When the switchingelement Q1 (or Q2) is ON, current flows from Vin, through L1 (or L2) andthen Q1 (or Q2), to Vin, so that an energy of the magnetic flux isaccumulated in the boost reactor L1 (or L2). When the switching elementQ1 (or Q2) is OFF, current flows from Vin through L1 (or L2), D1 (orD2), and Co, to Vin, so that the energy of the magnetic flux in theboost reactor L1 (or L2), which is accumulated during the ON time of theswitching element Q1 (or Q2), is discharged. This operation is expressedby the following expression:

$\begin{matrix}{{\Delta\;{IL}} = {{{\frac{Vin}{L} \cdot {Ton}}} \leq {{{\frac{{Vo} + {VF} - {Vin}}{L} \cdot {Toff}}}.}}} & {\Lambda(1)}\end{matrix}$

In the expression (1), ΔIL represents an amount of change in currentflowing through the boost reactor L1 (or L2), Vin the voltage across theinput power source Vin, Vo the voltage across the smoothing capacitorCo, VF the forward drop voltage of the rectifier D1 (or D2), L the valueof the inductance of the boost reactor L1 (or L2), Ton the ON time ofthe switching element Q1 (or Q2), and Toff the OFF time of the switchingelement Q1 (or Q2). The minimum value of the OFF time Toff of theswitching element Q1 (or Q2) is obtained from the expression (2) usingthe input voltage Vin, the output voltage Vo, and the ON time Ton:

$\begin{matrix}{{Toff} \geq {\frac{Vin}{{Vo} + {VF} - {Vin}} \cdot {{Ton}.}}} & {\Lambda(2)}\end{matrix}$

FIG. 2 is a chart showing the operation waveforms of components of theconventional interleaved converter. In FIG. 2, Vdr1 represents the drivesignal of the switching element Q1, Vc21 and Vc22 the voltages acrossthe phase control capacitors C21 and C22, respectively, Vdr2 the drivesignal of the switching element Q2, Vi1 the output signal of theswitching current detector CT1, Vi2 the output signal of the switchingcurrent detector CT2, Ii1 the current flowing through the reactor L1,Ii2 the current flowing through the reactor L2, Ii the input current ofthe interleaved converter, Id1 the current flowing through the rectifierD1, Id2 the current flowing through the rectifier D2, and Io the outputcurrent of the interleaved converter.

The first converter outputs the drive signal Vdr1 for driving theswitching element Q1, based on the output signal VFB of the voltagedetector 20 and the output signal Vi1 of the switching current detectorCT1, thereby converting the voltage from the input voltage Vin to theoutput voltage Vo. When the switching element Q1 is turned ON, the inputvoltage Vin is applied to the boost reactor L1, so that an energy of themagnetic flux is accumulated in the boost reactor L1. When the switchingelement Q1 is turned OFF, the energy of the magnetic flux accumulated inthe boost reactor L1 is charged to the smoothing capacitor Co throughthe rectifier D1.

In this manner, the first converter performs the power conversionthrough the path from the input power source Vin to the smoothingcapacitor Co by use of the ON/OFF operations of the switching elementQ1. In the same manner, the second converter performs the powerconversion through the path from the input power source Vin to thesmoothing capacitor Co by use of the ON/OFF operations of the switchingelement Q2. Operating the first converter and the second converterrespectively with mutually different phases suppresses the ripple of thecurrent flowing through the input power source Vin and the smoothingcapacitor Co. The suppressing effect is proportional to the number ofconverters connected in parallel with a constant phase differencebetween each two of the converters.

In the conventional example shown in FIG. 1, the charge/discharge device23 is provided to appropriately control the phase of each converter. Thecharge/discharge device 23 is configured to perform the charging anddischarging of the phase control capacitors C21 and C22 insynchronization with the drive signal Vdr1 of the switching element Q1.When the phase control capacitor C21 is charged, the phase controlcapacitor C22 is discharged. When the phase control capacitor C21 isdischarged, the phase control capacitor C22 is charged. The voltagesVc21 and Vc22 respectively across the phase control capacitors C21 andC22 form triangular waves having phases mutually shifted by 180 degrees.From the comparison of signals of the two triangular waves having phasesmutually shifted, it is found that the values of the voltages Vc21 andVc22 cross each other at the middle of each cycle of the drive signalVdr1 of the switching element Q1. The second control circuit 22 comparesthe inputted voltages Vc21 and Vc22 respectively across the phasecontrol capacitors C21 and C22 with each other, thereby detecting a timepoint at which the voltages Vc21 and Vc22 cross each other, and outputsthe drive signal Vdr2 to the switching element Q2 at the detected timepoint. With such a configuration, the second converter is given avoltage with a phase which is different by 180 degrees from that of thefirst converter.

However, in the interleaved converter configured as described above, thephase difference between the first and second converters varies due to adifference in capacity between the phase control capacitors C21 and C22.In addition, the interleaved converter requires phase control capacitorsthe number of which is equal to or larger than the number of convertersconnected in parallel. For this reason, an increase in the number ofconverters makes the circuit of the interleaved converter complicated.

An object of the present invention is thus to provide an inexpensiveinterleaved converter having a simplified circuit.

SUMMARY OF INVENTION

A first aspect of the present invention provides an interleavedconverter including: a parallel converter including a plurality ofconverters connected in parallel, each of the plurality of convertersincluding a reactor, a switching unit, and a rectifier; an input powersource configured to supply power to the parallel converter; a smoothingcapacitor configured to smooth an output of the parallel converter; aninput voltage detector configured to detect an input voltage of theparallel converter, and thereby to output an input voltage signal; anoutput voltage detector configured to detect an output voltage of theparallel converter, and thereby to output an output voltage signal; anda controller configured to control the parallel converter. In theinterleaved converter, the controller includes: an error amplifierconfigured to compare the output voltage signal with a referencevoltage, and thereby to output an error amplification signal; anarithmetic operator configured to perform arithmetic processing based onthe input voltage signal, the output voltage signal, and the erroramplification signal, and thereby to generate an ON time signal and anOFF time signal; a phase signal generator configured to generate aplurality of phase signals having mutually different phases, based onthe ON time signal, the OFF time signal, and the error amplificationsignal; a pulse generator configured to generate a plurality ofpulse-train signals synchronized respectively with the plurality ofphase signals, based on the ON time signal, the error amplificationsignal, and the plurality of phase signals; and a driver configured todrive the switching units in accordance with the plurality ofpulse-train signals.

In addition, a second aspect of the present invention provides aninterleaved converter including: a parallel converter including aplurality of converters connected in parallel, each of the plurality ofconverters including a reactor, a switching unit, and a rectifier; aninput power source configured to supply power to the parallel converter;a smoothing capacitor configured to smooth an output of the parallelconverter; an input voltage detector configured to detect an inputvoltage of the parallel converter, and thereby to output an inputvoltage signal; an output voltage detector configured to detect anoutput voltage of the parallel converter, and thereby to output anoutput voltage signal; and a controller configured to control theparallel converter. In the interleaved converter, the controllerincludes: an error amplifier configured to compare the output voltagesignal with a reference voltage, and thereby to output an erroramplification signal; an arithmetic operator configured to performarithmetic processing based on the input voltage signal, the outputvoltage signal, and the error amplification signal, and thereby togenerate an ON time signal and an OFF time signal; a phase signalgenerator configured to generate a plurality of phase signals havingmutually different phases, based on the ON time signal and the OFF timesignal;

a pulse generator configured to generate a plurality of pulse-trainsignals synchronized respectively with the plurality of phase signals,based on the ON time signal and the plurality of phase signals; and adriver configured to drive the switching units in accordance with theplurality of pulse-train signals.

BRIEF DESCRIPTION OF DRAWINGS

FIG. 1 is a circuit configuration diagram showing an example of aconventional interleaved converter.

FIG. 2 is a chart showing the operation waveforms of components of theconventional interleaved converter.

FIG. 3 is a circuit configuration diagram showing an interleavedconverter according to Embodiment 1 of the present invention.

FIG. 4 is a circuit configuration diagram showing an arithmetic operatorprovided in the interleaved converter according to Embodiment 1.

FIG. 5 is a circuit configuration diagram showing a multiplication anddivision circuit provided in the interleaved converter according toEmbodiment 1.

FIGS. 6A and 6B are graphs showing examples of waveforms indicatinginput/output characteristics of the arithmetic operator provided in theinterleaved converter according to Embodiment 1.

FIG. 7 is a circuit configuration diagram showing a phase signalgenerator provided in the interleaved converter according to Embodiment1.

FIG. 8 is a circuit configuration diagram showing a frequency dividercircuit in the phase signal generator shown in FIG. 7.

FIG. 9 is a chart showing the operation waveforms of components of thephase signal generator shown in FIG. 7.

FIG. 10 is a circuit configuration diagram showing a pulse generatorprovided in the interleaved converter according to Embodiment 1.

FIG. 11 is a chart showing the operation waveforms of components of thepulse generator shown in FIG. 10.

FIG. 12 is a circuit configuration diagram showing an interleavedconverter according to Embodiment 2 of the present invention.

FIG. 13 is a circuit configuration diagram showing an arithmeticoperator provided in the interleaved converter according to Embodiment2.

FIG. 14 is a circuit configuration diagram showing a phase signalgenerator provided in the interleaved converter according to Embodiment2.

FIG. 15 is a circuit configuration diagram showing a frequency dividercircuit in the phase signal generator shown in FIG. 14.

FIG. 16 is a chart showing the operation waveforms of components of thephase signal generator shown in FIG. 14.

FIG. 17 is a circuit configuration diagram showing a pulse generatorprovided in the interleaved converter according to Embodiment 2.

DESCRIPTION OF EMBODIMENTS

Hereinafter, an interleaved converter according to an embodiment of thepresent invention will be described in detail with reference to theaccompanying drawings. This interleaved converter is configured toimprove the power factor of power inputted from an input power source.

Embodiment 1

FIG. 3 is a circuit configuration diagram showing an interleavedconverter according to Embodiment 1 of the present invention. Afull-wave rectifier RC1 is configured to receive an AC voltage from anAC power source Vac, full-wave rectify the received AC voltage, andthereby output a DC voltage Vin. A first series circuit, which includesa boost reactor L1 and a switching element Q1 made of a MOSFET, isconnected to the output terminal of the full-wave rectifier RC1. Theanode of a rectifier D1 is connected to a connection point of the boostreactor L1 and the switching element Q1, and the cathode of therectifier D1 is grounded through a smoothing capacitor Co.

A second series circuit, which includes a boost reactor L2 and aswitching element Q2 made of a MOSFET, is connected to the outputterminal of the full-wave rectifier RC1. The anode of a rectifier D2 isconnected to a connection point of the boost reactor L2 and theswitching element Q2, and the cathode of the rectifier D2 is groundedthrough the smoothing capacitor Co.

A first voltage divider resistor including a resistor R1 and a resistorR2 is connected to the output terminal of the full-wave rectifier RC1. Asecond voltage divider resistor including a resistor R3 and a resistorR4 is connected to both terminals of the smoothing capacitor Co.

A control circuit 10 is configured to receive a midpoint voltage VIN ofthe first voltage divider resistor and a midpoint voltage VFB of thesecond voltage divider resistor, and to then output drive signals to thegates of the respective switching elements Q1 and Q2. The controlcircuit 10 includes an error amplifier 11, an arithmetic operator 12, aphase signal generator 13, a pulse generator 14, and a drive circuit 15.

The error amplifier 11 is configured to amplify an error between themidpoint voltage VFB of the second voltage divider resistor and areference voltage Vref, and to thereby output an error amplificationsignal VCOMP. The arithmetic operator 12 is configured to receive themidpoint voltage VIN of the first voltage divider resistor, the midpointvoltage VFB of the second voltage divider resistor, and the erroramplification signal VCOMP, to perform arithmetic operation on thesevoltages, and to thereby output an ON time signal Ion and an OFF timesignal Ioff. The ON time signal Ion is a signal proportional to the ONtime of the switching element Q1 (or Q2), and the OFF time signal Ioffis a signal proportional to the OFF time of the switching element Q1 (orQ2).

The phase signal generator 13 is configured to generate and output aphase signal Ph1 and a phase signal Ph2 having mutually differentphases, based on the ON time signal Ion, the OFF time signal Ioff, andthe error amplification signal VCOMP. The pulse generator 14 isconfigured to generate and output a pulse-train signal PWM1 and apulse-train signal PWM2 having the same duty ratio and mutuallydifferent phases, based on the phase signal Ph1, the phase signal Ph2,the ON time signal Ion, and the error amplification signal VCOMP. Thedrive circuit 15 is configured to generate a first drive signal Vdr1 fordriving the switching element Q1 and a second drive signal Vdr2 fordriving the switching element Q2, based on the pulse-train signals PWM1and PWM2, and to output the first drive signal Vdr1 and the second drivesignal Vdr2 to the corresponding switching elements.

The boost reactor L1, the switching element Q1, and the rectifier D1form a first converter. The boost reactor L2, the switching element Q2,and the rectifier D2 form a second converter. The first converter andthe second converter are connected to each other at the respective inputterminals as well as at the respective output terminals, thereby formingan interleaved converter.

The interleaved converter according to Embodiment 1 is configured toperform a power-factor improving operation to improve the power factorof an AC input current Iac inputted from an AC input power source Vac.The improving of the power factor requires for an input current tochange in proportion to an input voltage. The state of the input current(IL·Vin) during the power-factor improvement being performed areexpressed by the following expressions (3) and (4) obtained by modifyingthe expression (1):

$\begin{matrix}{{{{IL} \cdot {Vin}} = {{\frac{Vin}{L} \cdot {Ton}} = {\frac{{Vo} + {VF} - {Vin}}{L} \cdot {Toff}}}};} & {\Lambda(3)} \\{{IL} = {{\frac{1}{L} \cdot {Ton}} = {\frac{{Vo} + {VF} - {Vin}}{Vin} \cdot \frac{1}{L} \cdot {{Toff}.}}}} & {\Lambda(4)}\end{matrix}$

The ON time of a switching element changes in accordance with powerregardless of the phase of the input voltage. The OFF time of theswitching element can be obtained using the input voltage, the outputvoltage, and the ON time of the switching element.

When the ON time signal Ton and the OFF time signal Toff of theswitching element are generated in accordance with a constant currentcharge (or discharge) of a capacitor, the following expressions (5) and(6) are obtained:

$\begin{matrix}{{{Ton} = \frac{{Cosc} \cdot {VCOMP}}{Ion}};} & {\Lambda(5)} \\{{Toff} = {\frac{{Cosc} \cdot {VCOMP}}{Ioff}.}} & {\Lambda(6)}\end{matrix}$

In the expressions (5) and (6), Cosc represents an oscillator capacitor,VCOMP the error amplification signal, Ion the ON time signal, Ioff theOFF time signal. Since the ON time signal Ton of the switching elementvaries due to the error amplification signal VCOMP, the ON time signalIon is a constant or a function of the error amplification signal VCOMP.When the OFF time signal Ioff is obtained by substituting theexpressions (5) and (6) into the expression (2), the followingexpression (7) is obtained:

$\begin{matrix}{{Ioff} = {{Ion}{\frac{{Vo} + {VF} - {Vin}}{Vin}.}}} & {\Lambda(7)}\end{matrix}$

To put it differently, the OFF time signal Ioff is a value obtained bymultiplying the ON time signal Ion by a value obtained by dividing adifference between the output voltage Vo and the input voltage Vin bythe input voltage Vin.

FIG. 4 is a circuit configuration diagram showing the arithmeticoperator 12 provided in the interleaved converter according toEmbodiment 1 of the present invention. In FIG. 4, an operationalamplifier AP1 has a non-inverting input terminal connected to the erroramplification signal VCOMP, an output terminal connected to the gate ofa MOSFET Q10, and an inverting input terminal grounded through aresistor R10 and connected to the source of the MOSFET Q10. A currentsignal Ivcomp proportional to the error amplification signal VCOMP isoutputted from the drain of the MOSFET Q10 to a multiplication anddivision circuit 122 through a first current mirror circuit 121. Theoperational amplifier AP1 and the MOSFET Q10 form a firstvoltage/current converter circuit.

An operational amplifier AP2 has a non-inverting input terminalconnected to the midpoint voltage VIN of the first voltage dividerresistor, an output terminal connected to the gate of a MOSFET Q11, andan inverting input terminal grounded through a resistor R11 andconnected to the source of the MOSFET Q11. A current signal Ivinproportional to the midpoint voltage VIN of the first voltage dividerresistor is outputted from the drain of the MOSFET Q11 to amultiplication and division circuit 123. The operational amplifier AP2and the MOSFET Q11 form a second voltage/current converter circuit.

An operational amplifier AP3 has a non-inverting input terminalconnected to the midpoint voltage VFB of the second voltage dividerresistor, an output terminal connected to the gate of a MOSFET Q12, andan inverting input terminal grounded through a resistor R12 andconnected to the source of the MOSFET Q12. A current signal Ivfbproportional to the midpoint voltage VFB of the second voltage dividerresistor is outputted from the drain of the MOSFET Q12 to themultiplication and division circuit 123. The operational amplifier AP3and the MOSFET Q12 form a third voltage/current converter circuit.

In the first current mirror circuit 121, the collector and the base of atransistor Q13 as well as the base of a transistor Q14 are connected toform an input terminal of the first current mirror circuit 121. Theemitters of the respective transistors Q13 and Q14 are connected to apower source Reg. The collector of the transistor Q14 forms an outputterminal of the first current mirror circuit 121. The multiplication anddivision circuit 122 is configured to perform multiplication anddivision operations based on a constant current I10 and the currentsignal Ivcomp inputted from the first current mirror circuit 121 andbeing proportional to the error amplification signal VCOMP, and to thenoutput the ON time signal Ion as an output of the multiplication anddivision operations.

The multiplication and division circuit 123 is configured to performmultiplication and division operations based on the On time signal Ionfrom the multiplication and division circuit 122, the current signalIvin proportional to the midpoint voltage VIN of the first voltagedivider resistor, and the current signal Ivfb proportional to themidpoint voltage VFB of the second voltage divider resistor, and to thenoutput t+he OFF time signal Ioff as an output of the multiplication anddivision operations.

FIG. 5 is a circuit configuration diagram showing each of themultiplication and division circuits 122 and 123 provided in theinterleaved converter according to Embodiment 1. In FIG. 5, the base andthe collector of a transistor Q30 are connected to the power source Reg,and the emitter of the transistor Q30 is connected to an Ia inputterminal and the base of a transistor Q32. The collector of thetransistor Q32 is connected to the power source Reg, and the emitter ofthe transistor Q32 is connected to an Ib input terminal and the base ofa transistor Q34. The emitter of the transistor Q34 is connected to theemitter of a transistor Q35 and one end of a current source Itail.

The collector of the transistor Q34 is connected to the base of atransistor Q33 and the emitter of a transistor Q31. The base of thetransistor Q35 is connected to an Ic input terminal and the emitter ofthe transistor Q33. The collector of the transistor Q35 is connected toan Iout output terminal. The collector of the transistor Q33 isconnected to the power source Reg. The base and the collector of thetransistor Q31 are connected to the power source Reg. The transistorsQ30 to Q35 are NPN-type transistors, and form a multiplication anddivision circuit.

A value obtained by dividing a result of multiplication of an inputcurrent of the Ia input terminal and an input current of the Ib inputterminal by an input current of the Ic input terminal is outputted tothe Iout output terminal as a current signal. In addition, the maximumoutput of the Tout output terminal is limited to be less than thecurrent source Itail.

FIG. 6A and FIG. 6B are graphs showing examples of waveforms indicatingthe input/output characteristics of the arithmetic operator 12 providedin the interleaved converter according to Embodiment 1. FIG. 6A showshow the ON time signal Ion changes when the error amplification signalVCOMP is changed. The constant current I10 is inputted to the Ia inputterminal and the Ib input terminal of the multiplication and divisioncircuit 122, and the current signal Ivcomp is inputted to the Ic inputterminal of the multiplication and division circuit 122. The expressionfor the configuration of the multiplication and division circuit 122 is(current source I10)×(current source I10)/(current signal Ivcomp).Accordingly, the ON time signal Ion has such a characteristic as to beinversely proportional to the error amplification signal VCOMP.

FIG. 6B shows how the OFF time signal Ioff changes when the midpointvoltage VIN of the first voltage divider resistor is changed with themidpoint voltage VFB of the second voltage divider resistor beingmaintained at a constant value. The ON time signal Ion and aninput/output difference signal (Ivfb−Ivin) are inputted to the Ia inputterminal and the Ib input terminal of the multiplication and divisioncircuit 123. Here, the input/output difference signal (Ivfb−Ivin) isobtained by subtracting the current signal Ivin proportional to themidpoint voltage VIN of the first voltage divider resistor from thecurrent signal Ivfb proportional to the midpoint voltage VFB of thesecond voltage divider resistor. The current signal Ivin proportional tothe midpoint voltage VIN of the first voltage divider resistor isinputted to the Ic input terminal of the multiplication and divisioncircuit 123.

The expression for the configuration of the multiplication and divisioncircuit 123 is ON time signal Ion×input/output difference signal(Ivfb−Ivin)/(current signal Ivin proportional to the midpoint voltageVIN of the first voltage divider resistor). This expression isequivalent to that shown in the expression (7), so that the output ofthe multiplication and division circuit 123 becomes the OFF time signalIoff.

FIG. 7 is a circuit configuration diagram showing the phase signalgenerator 13 provided in the interleaved converter according toEmbodiment 1. In FIG. 7, an Ion input terminal is connected to the baseand the collector of a transistor Q40 as well as the base of atransistor Q41. The emitters of the transistors Q40 and Q41 areconnected to the power source Reg. The collector of the transistor Q41is connected to the source of a MOSFET Q44. The drain of the MOSFET Q44is connected to the drain of a MOSFET Q46, one terminal of an oscillatorcapacitor C1, a non-inverting input terminal of a comparator CP1, and aninverting input terminal of a comparator CP2. The gate of the MOSFET Q44is connected to the gate of the MOSFET Q46 and an inverted output Qb ofan RS flip-flop FF1.

The source of the MOSFET Q46 is connected to the collector of atransistor Q43. The base of the transistor Q43 is connected to the baseand the collector of a transistor Q42 as well as an Ioff input terminal.The emitters of the transistors Q42 and Q43 are grounded. The otherterminal of the oscillator capacitor C1 is grounded.

An inverting input terminal of the comparator CP1 is connected to aterminal for the error amplification signal VCOMP. An output terminal ofthe comparator CP1 is connected to a reset terminal of the RS flip-flopFF1. A non-inverting input terminal of the comparator CP2 is connectedto one terminal of a reference power source Vref. An output terminal ofthe comparator CP2 is connected to a set terminal of the RS flip-flopFF1.

An output Q of the RS flip-flop FF1 is connected to an input terminal ofa frequency divider circuit 132. The phase signal Ph1 and the phasesignal Ph2 are outputted from output terminals of the frequency dividercircuit 132, respectively. The transistor Q40 and the transistor Q41form a second current mirror circuit 131. The transistor Q42 and thetransistor Q43 form a third current mirror circuit. The MOSFET Q44 andthe MOSFET Q46 form a switching circuit.

FIG. 8 is a circuit configuration diagram showing the frequency dividercircuit 132 in the phase signal generator 13 shown in FIG. 7. In FIG. 8,an input terminal IN1 is connected to a T input of a T flip-flop FF2. Anoutput Q of the T flip-flop FF2 is connected to an input terminal of aninverter INV1, one of input terminals of an AND circuit AND2, an inputof a delay circuit DL1, and one of input terminals of an exclusive ORcircuit EOR1. An output terminal of the inverter INV1 is connected toone of input terminals of an AND circuit AND1. An output terminal of thedelay circuit DL1 is connected to the other one of the input terminalsof the exclusive OR circuit EOR1. An output terminal of the exclusive ORcircuit EOR1 is connected to the other one of the input terminals of theAND circuit AND2 and the other one of the input terminals of the ANDcircuit AND1. The first phase signal Ph1 is outputted from an outputterminal of the AND circuit AND1, and the second phase signal Ph2 isoutputted from an output terminal of the AND circuit AND2.

The T flip-flop FF2, the inverter INV1, the exclusive OR circuit EOR1,the delay circuit DL1, and the AND circuits AND1 and AND2 form afrequency divider circuit.

FIG. 9 is a chart showing the operation waveforms of the respectivecomponents of the phase signal generator 13 shown in FIG. 7. In FIG. 9,VCOMP represents the output voltage of the error amplifier 11, Vc1 thevoltage across the oscillator capacitor C1, Vref the output voltage ofthe reference power source Vref, CP1 the output signal of the comparatorCP1, CP2 the output signal of the comparator CP2, FF1Q the output Q ofthe RS flip-flop FF1, FF2Q the output Q of the T flip-flop FF2, EOR1 theoutput of the exclusive OR circuit EOR1, Ph1 the first phase signal Ph1,which is the output of the AND circuit AND1, Ph2 the second phase signalPh2, which is the output of the AND circuit AND2.

First of all, the ON time signal Ion and the OFF time signal Ioffgenerated by the arithmetic operator 12 are inputted to the phase signalgenerator 13. The ON time signal Ion and the OFF time signal Ioff thusinputted are sent to the oscillator capacitor C1 through the secondcurrent mirror circuit Q40 and Q41, the third current mirror circuit Q42and Q43, and the switching circuit Q44 and Q46.

The switching circuit Q44 and Q46 switches, in accordance with the stateof the RS flip-flop FF1, between the charging of the oscillatorcapacitor C1 according to the ON time signal Ion and the discharging ofthe oscillator capacitor C1 according to the OFF time signal Ioff.

When the RS flip-flop FF1 is in a set state, the inverted output Qb ofthe RS flip-flop FF1 is “L”. At this time, the MOSFET Q44 of theswitching circuit is in an ON state, and the MOSFET Q46 thereof is in anOFF state. Accordingly, the oscillator capacitor C1 is charged throughthe transistors Q40 and Q41 in accordance with the ON time signal Ion,so that the voltage Vc1 across the oscillator capacitor C1 increases.Once the voltage Vc1 across the oscillator capacitor C1 is charged to beequal to or higher than the error amplification signal VCOMP, the outputof the comparator CP1 switches from “L” to “H”, so that the RS flip-flopFF1 is reset.

When the RS flip-flop FF1 is reset, the inverted output Qb of the RSflip-flop FF1 is switched to “H”. At this time, the MOSFET Q44 of theswitching circuit is turned OFF, and the MOSFET Q46 thereof is turnedON. Accordingly, the electric charge accumulated in the oscillatorcapacitor C1 is discharged through the transistors Q42 and Q43 inaccordance with the OFF time signal Ioff, so that the voltage Vc1 acrossthe oscillator capacitor C1 decreases.

Once the voltage Vc1 across the oscillator capacitor C1 is discharged tobe equal to or lower than the reference voltage Vref, the output of thecomparator CP2 is switched from “L” to “H”, so that the RS flip-flop FF1is set again. The above-described operation is repeated to generate apulse train, which is then inputted to the frequency divider circuit132.

The pulse train inputted to the frequency divider circuit 132 is dividedin frequency by 2 by the T flip-flop FF2. The signal thus divided by theT flip-flop FF2 becomes a pulse train having a duty ratio ofapproximately 50% of that of the original inputted pulse train if thefrequency of the inputted pulse train does not change to a large extent.On the basis of the pulse train having a duty ratio of 50%, signalssynchronized respectively with each rising edge and each falling edgeare generated by the delay circuit DL1, the inverter INV1, the exclusiveOR circuit EOR1, and the AND circuits AND1 and AND2, and are thenoutputted as the first phase signal Ph1 and the second phase signal Ph2,respectively.

The phase signal generator 13 shown in FIG. 7 generates phase signalsfor controlling two converters. For this reason, the ON time signal Ionand the OFF time signal Ioff are each doubled in frequency or theoscillator capacitor C1 is adjusted to have a half value so that thefrequency of charge/discharge of the oscillator capacitor C1 should betwice the original oscillation frequency.

FIG. 10 is a circuit configuration diagram showing the pulse generator14 provided in the interleaved converter according to Embodiment 1. InFIG. 10, an input terminal for the ON time signal Ion is connected tothe base and the collector of a transistor Q50, the base of a transistorQ51, and the base of a transistor Q52. The emitters of the transistorsQ50, Q51, and Q52 are connected to the power source Reg. The collectorof the transistor Q51 is connected to one terminal of a first ON-timegenerator capacitor C2, the drain of a MOSFET Q54, and a non-invertinginput terminal of a comparator CP4.

The collector of the transistor Q52 is connected to one terminal of asecond ON-time generator capacitor C3, the drain of a MOSFET Q53, and anon-inverting input terminal of a comparator CP3.

An input terminal for the error amplification signal VCOMP is connectedto an inverting input terminal of the comparator CP3 and an invertinginput terminal of the comparator CP4. The other terminal of the firstON-time generator capacitor C2 is grounded. An output terminal of thecomparator CP4 is connected to a reset terminal of an RS flip-flop FF4.An input terminal for the first phase signal Ph1 is connected to thegate of the MOSFET Q54 and a set terminal of the RS flip-flop FF4. Thesource of the MOSFET Q54 is grounded. An output Q of the RS flip-flopFF4 is connected to an output terminal for the PWM1.

The other terminal of the second ON-time generator capacitor C3 isgrounded. An output terminal of the comparator CP3 is connected to areset terminal of an RS flip-flop FF3. An input terminal for the secondphase signal Ph2 is connected to the gate of the MOSFET Q53 and a setterminal of the RS flip-flop FF3. The source of the MOSFET Q53 isgrounded. An output Q of the RS flip-flop FF3 is connected to an outputterminal for the PWM2.

The comparator CP4, the first ON-time generator capacitor C2, the MOSFETQ54, and the RS flip-flop FF4 form a first ON-time generator circuit.The comparator CP3, the second ON-time generator capacitor C3, theMOSFET Q53, and the RS flip-flop FF3 form a second ON-time generatorcircuit.

FIG. 11 is a chart showing the operation waveforms of the respectivecomponents of the pulse generator 14 shown in FIG. 10. In FIG. 11, VCOMPrepresents the error amplification signal VCOMP, Vc1 the voltage acrossthe oscillator capacitor C1, Vref the voltage across the reference powersource Vref, Ph1 the first phase signal Ph1, Ph2 the second phase signalPh2, Vc2 the voltage across the first ON-time generator capacitor C2,Vc3 the voltage across the second ON-time generator capacitor C3, PWM1the first pulse-train signal, PWM2 the second pulse-train signal.

The ON time signal Ion inputted to the first ON-time generator circuit(or the second ON-time generator circuit) charges the first ON-timegenerator capacitor C2 (or the second ON-time generator capacitor C3)through the current mirror circuit formed of the transistors Q50, Q51,and Q52. Once the first phase signal Ph1 (or the second phase signalPh2) is inputted to the first ON-time generator circuit (or the secondON-time generator circuit), the MOSFET Q54 (or the MOSFET Q53) is turnedON, so that the electric charge accumulated in the first ON-timegenerator capacitor C2 (or the second ON-time generator capacitor C3) isdischarged and the RS flip-flop FF4 (or the RS flip-flop FF3) is set.

The first ON-time generator capacitor C2 (or the second ON-timegenerator capacitor C3) is charged in accordance with the ON time signalIon. Once the voltages Vc1 and Vc2 are increased to be equal to orhigher than the error amplification signal VCOMP, the output of thecomparator CP4 (or the comparator CP3) is switched to “H”. When theoutput of the comparator CP4 (or the comparator CP3) is switched to “H”,the RS flip-flop FF4 (or the RS flip-flop FF3) is reset.

Even after the RS flip-flop FF4 (or the RS flip-flop FF3) is reset, thefirst ON-time generator capacitor C2 (or the second ON-time generatorcapacitor C3) is continuously charged, so that the voltage across thefirst ON-time generator capacitor C2 (or the second ON-time generatorcapacitor C3) increases. Once the first phase signal Ph1 (or the secondphase signal Ph2) is inputted, the MOSFET Q54 (or the MOSFET Q53) isturned ON, so that the charge accumulated in the first ON-time generatorcapacitor C2 (or the second ON-time generator capacitor C3) isdischarged and the RS flip-flop FF4 (or the RS flip-flop FF3) is setagain. With the above-described operation repeated, the pulse generator14 generates a pulse train.

On the basis of the pulse trains having mutually different phases whichare generated by the pulse generator 14, the drive circuit 15 generatesdrive signals for driving the switching elements Q1 and Q2, and therebydrives the switching elements Q1 and Q2.

As described so far, since the phase signals are obtained from theresult of arithmetic operation on the input voltage, the output voltage,and the error amplification signal, favorable phase signals can begenerated even immediately after the start of operation. In addition, azero current state can be detected with no detecting of currents flowingthrough the reactors L1 and L2. For this reason, it is possible tosuppress, as much as possible, the complicating of a circuit due to anincrease in the number of converters connected in parallel withoutincreasing the number of peripheral components such as auxiliarywinding. As a result, an inexpensive interleaved converter can beprovided.

Embodiment 2

FIG. 12 is a circuit configuration diagram showing an interleavedconverter according to Embodiment 2 of the present invention. In FIG.12, a first series circuit, which includes a switching element Q1 madeof a MOSFET and a rectifier D3 made of a free-wheeling diode, isconnected to both terminals of an input power source Vin formed of a DCpower source. A step-down reactor L3 has one terminal connected to thecathode of the rectifier D3 and the other terminal grounded through asmoothing capacitor Co.

A second series circuit, which includes a switching element Q2 made of aMOSFET and a rectifier D4 made of a free-wheeling diode, is connected toboth terminals of the input power source Vin. A step-down reactor L4 hasone terminal connected to the cathode of the rectifier D4 and the otherterminal grounded through the smoothing capacitor Co.

A third series circuit, which includes a switching element Q3 made of aMOSFET and a rectifier D5 made of a free-wheeling diode, is connected toboth terminals of the input power source Vin. A step-down reactor L5 hasone terminal connected to the cathode of the rectifier D5 and the otherterminal grounded through the smoothing capacitor Co.

A first voltage divider resistor formed of a resistor R1 and a resistorR2 is connected to both terminals of the input power source Vin. Asecond voltage divider resistor formed of a resistor R3 and a resistorR4 is connected to both terminals of the smoothing capacitor Co. Acontrol circuit 10 a generates and outputs gate drive signals for theswitching elements Q1, Q2, and Q3 based on a midpoint voltage VIN of thefirst voltage divider resistor and a midpoint voltage VFB of the secondvoltage divider resistor.

The control circuit 10 a includes an error amplifier 11, an arithmeticoperator 12 a, a phase signal generator 13 a, a pulse generator 14 a,and a drive circuit 15 a. The arithmetic operator 12 a is configured toreceive the midpoint voltage VIN of the first voltage divider resistor,the midpoint voltage VFB of the second voltage divider resistor, and anerror amplification signal VCOMP from the error amplifier 11, andperform arithmetic operation on these voltages. With the output of thearithmetic operation, the arithmetic operator 12 a generates and outputsan ON time signal Ion and an OFF time signal Ioff. The ON time signalIon is a signal proportional to an ON time of the switching elements Q1,Q2, and Q3, and the OFF time signal Ioff is a signal proportional to anOFF time of the switching elements Q1, Q2, and Q3. The phase signalgenerator 13 a is configured to generate and output a first phase signalPh1, a second phase signal Ph2, and a third phase signal Ph3, based onthe ON time signal Ion and the OFF time signal Ioff.

The pulse generator 14 a is configured to generate and output a firstpulse-train signal PWM1, a second pulse-train signal PWM2, and a thirdpulse-train signal PWM3 having the same duty ratio and mutuallydifferent phases, based on the first phase signal Ph1, the second phasesignal Ph2, the third phase signal Ph3, and the ON time signal Ion. Thedrive circuit 15 a is configured to generate and output a first drivesignal Vdr1 for driving the switching element Q1, a second drive signalVdr2 for driving the switching element Q2, and a third drive signal Vdr3for driving the switching element Q3, based on the first pulse-trainsignal PWM1, the second pulse-train signal PWM2, and the thirdpulse-train signal PWM3

The switching element Q1, the rectifier D3, and the step-down reactor L3form a first converter. The switching element Q2, the rectifier D4, andthe step-down reactor L4 form a second converter. The switching elementQ3, the rectifier D5, and the step-down reactor L5 form a thirdconverter. The first converter, the second converter, and the thirdconverter are connected to one another at the respective input terminalsas well as at the respective output terminals, thereby forming a buckinterleaved converter.

The buck converter is configured to output an output voltage Vo that islower than an input voltage Vin, in accordance with the ON/OFFoperations of the switching elements. When the switching element Q1 (orQ2 or Q3) is ON, current flows from Vin, through Q1 (or Q2 or Q3), L3(or L4 or L5), and Co, to Vin in this order, so that an energy of themagnetic flux is accumulated in the step-down reactor L3 (or L4 or L5)and concurrently electric charge is accumulated in the smoothingcapacitor Co.

When the switching element Q1 (or Q2 or Q3) is OFF, current flows fromL3 (or L4 or L5), through Co and D3 (or D4 or D5), to L3 (or L4 or L5)in this order, so that the energy of the magnetic flux accumulated inthe step-down reactor L3 (or L4 or L5) is released. This operation isexpressed by the following expression:

$\begin{matrix}{{\Delta\;{IL}} = {{{\frac{{Vin} - {Vo}}{L} \cdot {Ton}}} \leq {{{\frac{{Vo} + {VF}}{L} \cdot {Toff}}}.}}} & {\Lambda(8)}\end{matrix}$

In the expression (8), ΔIL represents an amount of change in currentflowing through the step-down reactor L3 (or L4 or L5), Vin the voltageacross the input power source Vin, Vo the voltage across the smoothingcapacitor Co, VF the forward drop voltage of the rectifier D3 (or D4 orD5), L the inductance value of the step-down reactor L3 (or L4 or L5),Ton the ON time of the switching element Q1 (or Q2 or Q3), Toff the OFFtime of the switching element Q1 (or Q2 or Q3).

If the OFF time Toff in the expression (8) is obtained, the followingexpression (9) is obtained:

$\begin{matrix}{{Toff} = {\frac{{Vin} - {Vo}}{{Vo} + {VF}} \cdot {{Ton}.}}} & {\Lambda(9)}\end{matrix}$

Accordingly, as in the case of Embodiment 1, it is possible to obtainthe ON time Ton and the OFF time Toff of the switching elements Q1 toQ3, or the ON time signal Ion proportional to the ON time and the OFFtime signal Ioff proportional to the OFF time, by means of thearithmetic operator 12 a.

FIG. 13 is a circuit configuration diagram showing the arithmeticoperator 12 a provided in the interleaved converter according toEmbodiment 2. The arithmetic operator 12 a shown in FIG. 13 has aconfiguration formed by adding a resistor Ron and a resistor Roff to thearithmetic operator 12 shown in FIG. 4. The resistor Ron has oneterminal connected to an output terminal for the ON time signal Ion andthe other terminal grounded. The resistor Roff has one terminalconnected to an output terminal for the OFF time signal Ioff and theother terminal grounded.

The resistor Ron and the resistor Roff are configured to convert currentsignals into voltage signals for the ON time signal Ion and the OFF timesignal Ioff obtained by the arithmetic operation of the arithmeticoperator 12 a, respectively.

FIG. 14 is a circuit configuration diagram showing the phase signalgenerator 13 a provided in the interleaved converter according toEmbodiment 2. In the phase signal generator 13 a shown in FIG. 14, aconstant current source I61 has one terminal connected to the powersource Reg and the other terminal grounded through an oscillatorcapacitor C5. A comparator CP1 has an inverting input terminal connectedto the ON time signal Ion and a non-inverting input terminal connectedto a connection point of the constant current source I61 and theoscillator capacitor C5.

A constant current source I60 has one terminal connected to the powersource Reg and the other terminal grounded through an oscillatorcapacitor C4. A comparator CP2 has an inverting input terminal connectedto the OFF time signal Ioff and a non-inverting input terminal connectedto a connection point of the constant current source I60 and theoscillator capacitor C4. An RS flip-flop FF1 has a set terminalconnected to an output terminal of the comparator CP2 and a resetterminal connected to an output terminal of the comparator CP1.

A MOSFET Q60 has the drain connected to a connection point of theconstant current source I61 and the oscillator capacitor C5, the sourcegrounded, and the gate connected to an inverted output Qb of the RSflip-flop FF1. A MOSFET Q61 has the drain connected to a connectionpoint of the constant current source I60 and the oscillator capacitorC4, the source grounded, and the gate connected to an output Q of the RSflip-flop FF1. A frequency divider circuit 132 a is configured toreceive the output Q of the RS flip-flop FF1 and output phase signalsPh1, Ph2, and Ph3.

FIG. 15 is a circuit configuration diagram showing the frequency dividercircuit 132 a in the phase signal generator 13 a shown in FIG. 14. Inthe frequency divider circuit 132 a shown in FIG. 15, a T flip-flop FF2connected to an input terminal IN1, a T flip-flop FF2 a, and an ANDcircuit AND4 form a ternary counter. An output Q0 of the T flip-flopFF2, which corresponds to a least significant bit output of the ternarycounter, is connected to an input terminal of an AND circuit AND4 and aninput terminal of an AND circuit AND3.

An output Q1 a of the T flip-flop FF2 a, which corresponds to a mostsignificant bit output of the ternary counter, is connected to the otherinput terminal of the AND circuit AND4, an input terminal of a delaycircuit DL1, an input terminal of an AND circuit AND5, and an inputterminal of an exclusive OR circuit EOR1. An output terminal of thedelay circuit DL1 is connected to the other input terminal of theexclusive OR circuit EOR1. An output terminal of the exclusive ORcircuit EOR1 is connected to the other input terminal of the AND circuitAND5. The third phase signal Ph3 is outputted from an output terminal ofthe AND circuit AND5.

An output terminal of the AND circuit AND3 is connected to an inputterminal of a delay circuit DL2, an input terminal of an AND circuitAND6, and an input terminal of an exclusive OR circuit EOR2. An outputterminal of the delay circuit DL2 is connected to the other inputterminal of the exclusive OR circuit EOR2. An output terminal of theexclusive OR circuit EOR2 is connected to the other input terminal ofthe AND circuit AND6. The second phase signal Ph2 is outputted from anoutput terminal of the AND circuit AND6.

An inverted output Qb of the T flip-flop FF2 a, which is an invertedsignal of the most significant bit of the ternary counter, is connectedto an input terminal of a delay circuit DL3, an input terminal of an ANDcircuit AND7, and an input terminal of an exclusive OR circuit EOR3. Anoutput terminal of the delay circuit DL3 is connected to the other inputterminal of the exclusive OR circuit EOR3. An output terminal of theexclusive OR circuit EOR3 is connected to the other input terminal ofthe AND circuit AND7. The first phase signal Ph1 is outputted from anoutput terminal of the AND circuit AND7.

FIG. 17 is a circuit configuration diagram showing the pulse generator14 a provided in the interleaved converter according to Embodiment 2. InFIG. 17, an input terminal for the ON time signal Ion is connected toinverting input terminals of comparators CP3, CP4, and CP5. A terminalof each of constant current sources 120, 121, and 122 is connected tothe power source Reg.

The other terminal of the constant current source I22 is connected toone terminal of a first ON-time generator capacitor C11, the drain of aMOSFET Q53, and a non-inverting input terminal of the comparator CP3.The other terminal of the first ON-time generator capacitor C11 and thesource of the MOSFET Q53 are grounded. The other terminal of theconstant current source I21 is connected to one terminal of a secondON-time generator capacitor C12, the drain of a MOSFET Q54, and anon-inverting input terminal of the comparator CP4. The other terminalof the second ON-time generator capacitor C12 and the source of theMOSFET Q54 are grounded. The other terminal of the constant currentsource I20 is connected to one terminal of a third ON-time generatorcapacitor C13, the drain of a MOSFET Q55, and a non-inverting inputterminal of the comparator CP5. The other terminal of the third ON-timegenerator capacitor C13 and the source of the MOSFET Q55 are grounded.

An output terminal of the comparator CP3 is connected to a resetterminal of an RS flip-flop FF3. An input terminal for the first phasesignal Ph1 is connected to a set terminal of the RS flip-flop FF3. Anoutput Q of the RS flip-flop FF3 is connected to an output terminal forthe PWM1. An inverted output Qb of the RS flip-flop FF3 is connected tothe gate of the MOSFET Q53.

An output terminal of the comparator CP4 is connected to a resetterminal of an RS flip-flop FF4. An input terminal for the second phasesignal Ph2 is connected to a set terminal of the RS flip-flop FF4. Anoutput Q of the RS flip-flop FF4 is connected to an output terminal forthe PWM2. An inverted output Qb of the RS flip-flop FF4 is connected tothe gate of the MOSFET Q54.

An output terminal of the comparator CP5 is connected to a resetterminal of an RS flip-flop FF5. An input terminal for the third phasesignal Ph3 is connected to a set terminal of the RS flip-flop FF5. Anoutput Q of the RS flip-flop FF5 is connected to an output terminal forthe PWM3. An inverted output Qb of the RS flip-flop FF5 is connected tothe gate of the MOSFET Q55.

The comparator CP3, the first ON-time generator capacitor C11, theMOSFET Q53, and the RS flip-flop FF3 form a first ON-time generatorcircuit. The comparator CP4, the second ON-time generator capacitor C12,the MOSFET Q54, and the RS flip-flop FF4 form a second ON-time generatorcircuit. The comparator CP5, the third ON-time generator capacitor C13,the MOSFET Q55, and the RS flip-flop FF5 form a third ON-time generatorcircuit. The phase signal generator 13 a is configured to generate phasesignals for controlling three comparators. For this reason, the currentvalues of the constant current sources 160 and 161 are adjusted or eachof the oscillator capacitors C4 and C5 is adjusted to have an one-thirdvalue so that the frequency of charge/discharge of each of theoscillator capacitors C4 and C5 should be three times as the originaloscillation frequency.

FIG. 16 is a chart showing the operation waveforms of the respectivecomponents of the phase signal generator 13 a. In FIG. 16, Ionrepresents the ON time signal Ion, Vc4 the voltage across the oscillatorcapacitor C4, Ioff the OFF time signal Ioff, Vc5 the voltage across theoscillator capacitor C5, CP1 the output signal of the comparator CP1,CP2 the output signal of the comparator CP2, FF2Q the output signal ofthe RS flip-flop FF2, Q0 the least significant bit output of the ternarycounter, Q1 a the most significant bit output of the ternary counter,Ph1 the first phase signal, Ph2 the second phase signal, Ph3, the thirdphase signal, Vc11 the voltage across the first ON-time generatorcapacitor C11, Vc12 the voltage across the second ON-time generatorcapacitor C12, Vc13 the voltage across the third ON-time generatorcapacitor C13, PWM1 the first pulse-train signal, PWM2 the secondpulse-train signal, PWM3 the third pulse-train signal.

Next, the operation of the phase signal generator 13 a will be describedwith reference to FIG. 16. First, when the RS flip-flop FF1 is in a setstate, the MOSFET Q61 is ON and the MOSFET Q60 is OFF. Since the MOSFETQ61 is ON, the oscillator capacitor C4 is discharged. On the other hand,since the MOSFET Q60 is OFF, the oscillator capacitor C5 is charged bythe constant current source I61, so that the voltage across theoscillator capacitor C5 increases.

Once the voltage across the oscillator capacitor C5 is increased to beequal to or higher than the potential of the ON time signal Ion, theoutput of the comparator CP1 is switched from “L” to “H”, so that the RSflip-flop FF1 is reset. When the RS flip-flop FF1 is reset, the MOSFETQ60 is turned ON, so that the oscillator capacitor C5 is discharged andthe MOSFET Q61 is turned OFF.

When the MOSFET Q61 is turned OFF, the oscillator capacitor C4 ischarged by the constant current source I60. Once the voltage across theoscillator capacitor C4 is increased to be equal to the potential of theOFF time signal Ioff, the comparator CP2 is switched from “L” to “H”, sothat the RS flip-flop FF1 is set. The above-described operation isrepeated, so that a pulse-train signal is outputted from the outputterminal of the RS flip-flop FF1. The pulse-train signal varies in theratio and frequencies of the “H” level and the “L” level depending onthe ON time signal Ion and the OFF time signal Ioff, respectively.

When inputted to the frequency divider circuit 132 a, the output signalof the RS flip-flop FF1 is divided by 3 by the ternary counter, therebybeing converted into a digital signal having the most significant bit Q1a and the least significant bit Q0. The digital signal thus obtainedthrough the conversion is converted into the phase signals Ph1, Ph2,Ph3, having phases mutually shifted by approximately 120 degrees, by thefrequency divider circuit 132 a formed of the AND circuits ANDS to AND7,the exclusive OR circuits EOR1 to EOR3, and the delay circuits DL1 toDL3.

Each of the phase signals Ph1, Ph2, and Ph3 is inputted to the pulsegenerator 14 a shown in FIG. 17, so that the pulse-train signals PWM1,PWM2, and PWM3 having mutually different phases are generated. Thepulse-train signals PWM1, PWM2, and PWM3 are converted respectively intothe drive signals Vdr1, Vdr2, and Vdr3 for driving the switchingelements Q1 to Q3 by the drive circuit 15 a. As a result, theinterleaved converter is operated.

As described so far, the interleaved converter according to Embodiment 2provides the same advantageous effects as those provided by theinterleaved converter according to Embodiment 1.

It should be noted that the present invention is not limited toEmbodiments 1 and 2 described so far. Although the analogue arithmeticoperators are used as the arithmetic operators 12 and 12 a inEmbodiments 1 and 2, digital arithmetic operators may be used instead.In addition, the converter circuits may be buck boost converters insteadof the boost converters and the buck converters. Alternatively, theconverter circuits may be forward converters, flyback converters, orresonant converters. Moreover, although the forward step-down voltagesof the rectifiers D1 to D5 are omitted in the arithmetic operators 12and 12 a, correction signals may be added in consideration of theforward step-down voltages.

Furthermore, even if the number of converters connected in parallel isincreased, the present invention may be adapted by setting theoscillation frequency of each oscillator capacitor as a high frequencysuitable for the number of converters and by increasing the number bywhich the frequency is divided by the frequency divider circuit.

According to the present invention, since the phase signal is obtainedfrom the result of arithmetic operation on the input voltage, the outputvoltage, and the error amplification signal, favorable phase signals canbe generated immediately after the start of operation. In addition, azero current state can be detected with no detecting of currents flowingthrough the reactors. For this reason, it is possible to suppress, asmuch as possible, the complicating of a circuit due to an increase inthe number of converters connected in parallel without increasing thenumber of peripheral components such as auxiliary winding. As a result,an inexpensive interleaved converter can be provided.

The present invention may be employed as a control system for the casewhere multiple converters are connected in parallel and controlled withmutually shifted phases.

1. An interleaved converter comprising: a parallel converter including aplurality of converters connected in parallel, each of the plurality ofconverters including a reactor, a switching unit, and a rectifier; aninput power source configured to supply power to the parallel converter;a smoothing capacitor configured to smooth an output of the parallelconverter; an input voltage detector configured to detect an inputvoltage of the parallel converter, and thereby to output an inputvoltage signal; an output voltage detector configured to detect anoutput voltage of the parallel converter, and thereby to output anoutput voltage signal; and a controller configured to control theparallel converter, wherein the controller includes: an error amplifierconfigured to compare the output voltage signal with a referencevoltage, and thereby to output an error amplification signal; anarithmetic operator configured to perform arithmetic processing based onthe input voltage signal, the output voltage signal, and the erroramplification signal, and thereby to generate an ON time signal and anOFF time signal; a phase signal generator configured to generate aplurality of phase signals having mutually different phases, based onthe ON time signal, the OFF time signal, and the error amplificationsignal; a pulse generator configured to generate a plurality ofpulse-train signals synchronized respectively with the plurality ofphase signals, based on the ON time signal, the error amplificationsignal, and the plurality of phase signals; and a driver configured todrive the switching units in accordance with the plurality ofpulse-train signals.
 2. The interleaved converter according to claim 1,wherein the phase signal generator includes: a signal generatorconfigured to generate a signal having a frequency of n times thefrequency of a signal generated based on the ON time signal, the OFFtime signal, and the error amplification signal; and a frequency dividerconfigured to divide the signal outputted from the signal generator byn, and thereby to output n phase signals having mutually differentphases.
 3. The interleaved converter according to claim 1, wherein thearithmetic operator generates the ON time signal based on the erroramplification signal, and generates the OFF time signal based on theinput voltage signal, the output voltage signal, and the ON time signal.4. An interleaved converter comprising: a parallel converter including aplurality of converters connected in parallel, each of the plurality ofconverters including a reactor, a switching unit, and a rectifier; aninput power source configured to supply power to the parallel converter;a smoothing capacitor configured to smooth an output of the parallelconverter; an input voltage detector configured to detect an inputvoltage of the parallel converter, and thereby to output an inputvoltage signal; an output voltage detector configured to detect anoutput voltage of the parallel converter, and thereby to output anoutput voltage signal; and a controller configured to control theparallel converter, wherein the controller includes: an error amplifierconfigured to compare the output voltage signal with a referencevoltage, and thereby to output an error amplification signal; anarithmetic operator configured to perform arithmetic processing based onthe input voltage signal, the output voltage signal, and the erroramplification signal, and thereby to generate an ON time signal and anOFF time signal; a phase signal generator configured to generate aplurality of phase signals having mutually different phases based on theON time signal and the OFF time signal; a pulse generator configured togenerate a plurality of pulse-train signals synchronized respectivelywith the plurality of phase signals, based on the ON time signal and theplurality of phase signals; and a driver configured to drive theswitching units in accordance with the plurality of pulse-train signals.5. The interleaved converter according to claim 4, wherein the phasesignal generator includes: a signal generator configured to generate asignal having a frequency of n times the frequency of a signal generatedbased on the ON time signal and the OFF time signal; and a frequencydivider configured to divide the signal outputted from the signalgenerator by n, and thereby to output n phase signals having mutuallydifferent phases.
 6. The interleaved converter according to claim 4,wherein the arithmetic operator generates the ON time signal based onthe error amplification signal, and generates the OFF time signal basedon the input voltage signal, the output voltage signal, and the ON timesignal.